Phase locked loop with sub-harmonic locking prevention functionality

ABSTRACT

Embodiments relate to type-I PLLs that do not lock at a sub-harmonic frequency of a reference clock signal by controlling timing of charging or discharging of one or more capacitors in the PLLs. A phase frequency detector (PFD) of a type-I PLL can prevent sub-harmonic locking by generating a clear output signal to cause a sampling capacitor of PLL&#39;s loop filter to discharge only during a time period when the sampling capacitor is not being charged. For example, the PFD can include a gating element to control the time during which the clear output signal is generated. By ensuring that the sampling capacitor is not discharged during a time period while it is being charged, the PLL&#39;s voltage-controlled oscillator is controlled to oscillate at an intended frequency rather than at a sub-harmonic of the intended frequency.

BACKGROUND

Field of the Disclosure

This disclosure pertains in general to phase locked loops (PLLs) andmore particularly to a sample and reset type-I PLL.

Description of the Related Art

PLLs are widely employed in radio, telecommunications, computers, andother electronic applications. They can be used to demodulate a signal,recover a signal from a noisy communication channel, generate a stablefrequency at multiples of an input frequency (frequency synthesis), ordistribute precisely timed clock pulses in digital logic circuits suchas microprocessors. Since a single integrated circuit can provide acomplete PLL functionality, PLLs are widely used in modern electronicdevices, with output frequencies ranging from a few hertz up to manygigahertz.

PLLs can be implemented as either a type-I PLL or a type-II PLL. Type-IIPLL typically uses a large capacitor for improving stability of theloop, which increases the die cost and also causes leakage currentissues as the technology scales down to deep sub-micron CMOS processtechnologies. A type-I PLL can reduce leakage current issues byimplementing a linear phase detection and also by eliminating the largecapacitor for stability. A drawback of conventional type-I PLLs issub-harmonic locking, where the type-I PLL locks the loop to a frequencyof the divider clock signal that is a sub-harmonic value of a frequencyof an oscillator output signal of a voltage-controlled oscillator (VCO).Conventional type-I PLLs use a separate frequency detector loop thatprevents the PLL from sub-harmonic locking by ensuring that the VCOoscillates at the proper frequency.

SUMMARY

Embodiments relate to a PLL where sub-harmonic locking is prevented. ThePLL can include a mechanism for generating a charge output signal thatoperates to prevent locking of the PLL at a sub-harmonic of a frequencyof an oscillator output signal by controlling timing during which one ormore capacitors in the PLL is charged or discharged.

In one embodiment, the PLL can further include a loop filter thatincludes a sampling capacitor and a holding capacitor coupled inparallel via a switching element. The loop filter can generate a filteroutput signal based at least on the charge output signal indicating afirst time period during which the sampling capacitor is charged. ThePLL can also include a voltage controlled oscillator (VCO) coupled tothe loop filter and can generate an oscillator output signal with afrequency corresponding to the filter output signal. The PLL can furtherinclude a divider coupled to the VCO to receive the oscillator outputsignal. The divider can perform frequency division on the oscillatoroutput signal to generate a divider clock signal having a same phase asthe oscillator output signal but a different frequency than theoscillator output signal. The PLL can also include a phase frequencydetector (PFD) coupled to the divider to receive the divider clocksignal. The PFD can generate the charge output signal based on a phasedifference between the divider clock signal and the reference clocksignal.

In one embodiment, the PFD can include a gating element to generate aclear output signal causing the sampling capacitor to discharge chargeto a low reference voltage of the loop filter during a second timeperiod different from the first time period.

In one embodiment, the gating element can include a digital gateperforming a logical AND operation.

In one embodiment, a sum of the first time period and the second timeperiod is equal to one half period of the reference clock signal.

In one embodiment, the second time period is defined as a period duringwhich a charge is not transferred between the sampling capacitor and theholding capacitor via the switching element. During the second timeperiod, each of the divider clock signal and the reference clock signalis inactive.

In one embodiment, the PFD can further generate a transfer output signalcausing a transfer of charge between the sampling capacitor and theholding capacitor during a third time period different from the secondtime period.

In one embodiment, the third time period is defined by a pulse width ofthe transfer output signal. The pulse width of the transfer outputsignal increases as the phase difference increases and the pulse widthof the transfer signal decreases as the phase difference decreases.

In one embodiment, a sum of the first time period, the second timeperiod, and the third time period is less than a period of the referenceclock signal.

In one embodiment, a sum of the second time period and the third timeperiod is equal to one half period of the reference clock signal.

In one embodiment, the first time period is defined by a pulse width ofthe charge output signal. The pulse width of the charge output signalincreases as the phase difference increases and the pulse width of thecharge signal decreases as the phase difference decreases.

Embodiments also relate to operating a PLL to generate a charge outputsignal to charge a sampling capacitor during a first time period set toprevent locking of the PLL at a frequency that is a sub-harmonic of afrequency of an oscillator output signal.

In one embodiment, a filter output signal can be generated based atleast on a charge output signal by a loop filter and an oscillatoroutput signal with a frequency corresponding to the filter output signalcan be generated by a voltage controlled oscillator. A divider clocksignal can be generated by performing a frequency division on theoscillator output signal at a divider. The divider clock signal has thesame phase as the oscillator output signal but has a frequency differentthan the oscillator output signal.

Embodiments also relate to a non-transitory computer-readable mediumstoring a digital representation of the PLL that can preventsub-harmonic locking by controlling timing during which one or morecapacitors in the PLL is charged or discharged.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a high-level block diagram of a Phase-Locked Loop (PLL),according to one embodiment.

FIG. 2 is a block diagram of a charge pump and a sample-reset loopfilter of a type-I PLL, according to one embodiment.

FIG. 3 is a timing diagram illustrating an operation of the charge pumpand the sample-reset loop filter, according to one embodiment.

FIG. 4 is a timing diagram illustrating a sub-harmonic locking of a PLL,according to one embodiment.

FIG. 5A is a block diagram illustrating a first portion of aphase/frequency detector (PFD) of a type-I PLL, according to oneembodiment.

FIG. 5B is a block diagram illustrating a second portion of the PFD,according to one embodiment.

FIG. 6 is a flowchart illustrating a process of operating a type-I PLL,according to one embodiment.

FIG. 7 is a block diagram illustrating an electronic device that storesa representation of a type-I PLL, according to one embodiment.

DETAILED DESCRIPTION

The Figures (FIGS.) and the following description relate to variousembodiments by way of illustration only. It should be noted that fromthe following discussion, alternative embodiments of the structures andmethods disclosed herein will be readily recognized as viablealternatives that may be employed without departing from the principlesdiscussed herein. Reference will now be made in detail to severalembodiments, examples of which are illustrated in the accompanyingfigures. It is noted that wherever practicable similar or like referencenumbers may be used in the figures and may indicate similar or likefunctionality.

Embodiments of the present disclosure relate to type-I phase lockedloops (PLLs) that do not lock at a sub-harmonic frequency of anoscillator output signal by controlling timing of charging ordischarging of one or more capacitors in the PLLs. A phase frequencydetector (PFD) of a type-I PLL can prevent sub-harmonic locking of thePLL by generating a clear output signal to cause a sampling capacitor ofPLL's loop filter to discharge only during a time period when thesampling capacitor is not being charged. For example, the PFD caninclude a gating element to control the time during which the clearoutput signal is generated. By ensuring that the sampling capacitor isnot discharged during a time period while it is being charged, theoutput of the loop filter is maintained at a level that causes PLL'svoltage-controlled oscillator (VCO) to oscillate at an intendedfrequency rather than at a sub-harmonic of the intended frequency.

The term “active voltage level” described herein refers to a voltagelevel corresponding to a logical high level. For example, in a digitalcircuit with supply voltage VDD and ground voltage GND, an activevoltage level is VDD or within a noise margin of VDD.

The term “inactive voltage level” described herein refers to a voltagelevel that corresponds to a logical low level. For example, an inactivevoltage level is GND or within a noise margin of GND.

In a normal mode of operation, a PLL phase locks at an intendedfundamental frequency of an oscillator output signal of the PLL's VCO.Due to non-idealities of the PLL, the PLL can undesirably phase lock ata sub-harmonic frequency of the oscillator output signal. For example,the VCO can generate an oscillator output signal at a frequencycorresponding to a sub-harmonic of the intended fundamental frequency ofoscillator output signal due to non-idealities of the PLL, which maycause the PLL to phase lock to the sub-harmonic frequency of theintended VCO output signal.

One technique to prevent the PLL from sub-harmonic locking is to use afrequency detector loop that assists the PLL to lock to an intendedfrequency that is a fundamental frequency of the VCO output signal. Thefrequency detector loop includes some components of the PLL and alsoincludes some other components that are not part of the PLL. Thecomponents of the PLL included in the frequency detector loop caninclude loop filter, VCO, and frequency divider. The components that arenot part of the PLL can include a frequency detector, a second chargepump that is separate from the PLL's charge pump, and control logic.While operating the frequency detector loop, the PLL is placed in anopen loop configuration by disabling its phase detector. Instead ofusing the PLL's phase detector, the frequency detector loop uses thefrequency detector, whose output signal is feed into the second chargepump. The frequency detector loop is further operated by feeding thesecond charge pump's output into the PLL's loop filter, and subsequentlyto the VCO, and the frequency divider. The frequency detector loop iscompleted when a divider clock signal (i.e., output of the frequencydivider) and the reference clock signal are fed into the frequencydetector. By comparing frequencies of the reference clock signal and thedivider clock signals, the frequency detector loop can ensure that theVCO is oscillating at the desired frequency. After the frequency lockingprocess is completed, the PLL is switched back to the closed loopconfiguration to perform phase locking, while the frequency detectorloop is disabled.

Other techniques to prevent the PLL from sub-harmonic locking aredescribed below with reference to FIGS. 2 through 5.

FIG. 1 is a high-level block diagram of a PLL, according to oneembodiment. PLL 100 receives a reference clock signal 105 as an inputand generates an output clock signal 135 that has the same phase asreference clock signal 105. For this purpose, PLL 100 includes, amongother components, phase detector 110, loop filter 120, VCO 130, andfrequency divider 140.

Phase detector 110 compares a phase of reference clock signal 105 and afrequency divided version (i.e., clock signal 145) of output clocksignal 135. Phase detector 110 determines a phase difference betweenreference clock signal 105 and divider clock signal 145, and generatesphase error signal 115. A type-I PLL typically uses a unipolar phasedetector that generates phase error signal 115 only during a conditionwhen reference clock signal 105 either leads or lags divider clocksignal 155 but not for both conditions. In one embodiment, the unipolarphase detector generates phase error signal 115 only when referenceclock signal 105 leads divider clock signal 145. Alternatively, theunipolar phase detector generates phase error signal 115 only whenreference clock signal 105 lags divider clock signal 145. In someembodiments, phase detector can also implement a frequency detectionfeature whereby the phase detector becomes a phase/frequency detector(PFD).

Phase error signal 115 is input to a loop filter 120. In one embodiment,loop filter 120 is a low pass filter that filters out the high frequencycomponents of the phase error signal and generates a control voltagesignal 125 that is fed to VCO 130. The cutoff frequency of loop filter120 determines the stability of the PLL. The characteristics of loopfilter 120 determine how the PLL responds to non-ideal variations suchas jitter in the reference clock signal 105. For example, if referenceclock signal 105 includes jitter, it may be advantageous to design loopfilter 120 so that the jitter is not propagated to the output of thePLL.

Typically, a loop filter of a PLL has a cutoff frequency that is smallerthan one tenth of the frequency of reference clock signal 105. Thecutoff frequency of loop filter 120 is controlled by a capacitance valueof a capacitor used in loop filter 120. Capacitors with largecapacitance values occupy a large area in PLLs and, as such, mayincrease the cost of manufacturing the integrated circuits (ICs) thatinclude PLLs. For example, a capacitor may occupy 90% of the area of aloop filter, and the loop filter may occupy around 50% of the area of aPLL. In one embodiment, loop filter 120 includes a charge pumpfunctionality. A PLL charge pump can be a CMOS or bipolar switchedcurrent source that outputs positive and negative current pulses intoloop filter 120. A type-I PLL typically uses a unipolar charge pump thatoutputs either a positive or negative current pulse into loop filter120. An exemplary loop filter is described below in detail withreference to FIG. 2.

VCO 130 receives control voltage signal 125 from loop filter 120 andgenerates a periodic output signal based on a voltage level of controlvoltage signal 125. Frequency divider 140 receives output clock signal135 from VCO 130 and generates divider clock signal 145 that is fed intophase detector 110. Frequency divider 140 performs frequency division onoutput clock signal 135 to generate divider clock signal 145 that hasthe same phase as output clock 135 but has a frequency different thanoutput clock signal 135. In some embodiments, frequency divider 140 maydivide the frequency of output clock signal 135 by an integer. Forinstance, frequency divider 140 may generate one period of divider clocksignal 145 for every N cycles of output clock signal 135. That is, thefrequency of output clock signal 135 is divided by N. Alternatively, thefrequency of output clock signal 135 can be divided by a fraction of aninteger to implement a Frac-N divider and a Frac-N PLL.

FIG. 2 is a block diagram of a charge pump and a sample-reset loopfilter of a type-I PLL, according to one embodiment. Charge pump 210includes a constant current source Ip that functions as a source forcurrent into switched-capacitor based sample-hold-reset (SHR) loopfilter 220 (hereinafter “SHR loop filter”). SHR loop filter 220includes, among other components, switches S1 through S3, samplingcapacitor C1, and holding capacitor C2. Switch S1 is controlled by asignal CHRG to charge sampling capacitor C1. The voltage levelcorresponding to a charge of sampling capacitor C1 is represented by Vx.CHRG signal is generated by phase detector 110 such that a pulse widthof CHRG signal increases as a phase difference between reference clocksignal 105 and divider clock signal 145 increases. Additionally, thepulse width of CHRG signal decreases as the phase difference decreases.

Switch S3 is controlled by a signal TRANS to transfer a charge betweensampling capacitor C1 and holding capacitor C2. The voltage levelcorresponding to a charge of holding capacitor C2 is represented by Vo.TRANS signal is generated by phase detector 110 such that a pulse widthof TRANS signal increases as a phase difference between reference clocksignal 105 and divider clock signal 145 increases. Additionally, thepulse width of TRANS signal decreases as the phase difference decreases.Switch S2 is controlled by a signal CLR that is also generated by phasedetector 110 to discharge (or reset) a charge of sampling capacitor C1to a low reference voltage of SHR loop filter 220.

FIG. 3 is a timing diagram illustrating an operation of charge pump 210and SHR loop filter 220, according to one embodiment. In FIG. 3, x-axisrepresents time and y-axis represents voltage of various signals. Timeaxis includes various points in time, t1 through t12, represented byvertical dotted lines. FIG. 3 shows reference clock signal 105 asREF_CLK and divider clock signal 145 as DIV_CLK. The time period betweenpoints t1 and t5 constitutes one period of REF_CLK. Time between pointst1 and t5 represent a first period of REF_CLK and time between t5 and t9represents a second period of REF_CLK. In FIG. 3, REF_CLK leads DIV_CLKas the first rising edge of REF_CLK occurs at t1 before the first risingedge of DIV_CLK occurs at t2.

SHR loop filter 220 generates voltage signals Vx and Vo only whenREF_CLK leads DIV_CLK. Alternatively, SHR loop filter 220 can beimplemented to generate voltage signals Vx and Vo only when REF_CLK lagsDIV_CLK.

Phase detector (e.g., phase detector 110) generates signals CHRG, TRANS,and CLR based on input signals, REF_CLK and DIV_CLK. CHRG signal is usedto control time at which sampling capacitor C1 is charged. CHRG isgenerated to represent a first time period signifying the phasedifference between the rising edges of REF_CLK and DIV_CLK. For example,CHRG signal is at an active voltage level (e.g., close to supply voltageVDD) between points t1 and t2 that represents a difference in the risingedges for REF_CLK and DIV_CLK. CLR signal is used to control switch S2to discharge a charge of sampling capacitor C1 to a low referencevoltage of SHR loop filter 220. CLR signal is generated to represent asecond time period when each of the signals, REF_CLK, DIV_CLK, and TRANSis at an inactive voltage level (i.e., a voltage level close to groundvoltage GND). For example, CLR signal has an active voltage levelbetween points t4 and t5 that represents a time period when each ofREF_CLK, DIV_CLK, and TRANS signals is at an inactive voltage level.

TRANS signal is used to transfer a charge between sampling capacitor C1and holding capacitor C2. TRANS is generated to represent a third timeperiod signifying a phase difference between the falling edges ofREF_CLK and DIV_CLK. For example, TRANS signal has an active voltagelevel between points t3 and t4 that represents a time difference in thefalling edges for REF_CLK and DIV_CLK.

In some embodiments, a sum of the first time period (i.e., CHRG at anactive voltage level) and the second time period (i.e., CLR at an activevoltage level) is equal to one half period value of REF_CLK. Forexample, the sum of the first and second time periods is represented bya sum of time periods between points t1 and t2, and points t4 and t5.When REF_CLK and DIV_CLK both have a 50% duty cycle, the first timeperiod is same as the third time period. A sum of the third time period(i.e., between points t3 and t4) and the second time period (i.e.,between points t4 and t5) is represented between points t3 and t5. Thetime period between points t3 and t5 represents a time period whenREF_CLK is at an inactive voltage level. Because REF_CLK's duty cycle is50%, a time period for inactive voltage level is the same as the timeperiod for active voltage level, and time period between points t3 andt5 is one half period of REF_CLK.

Alternatively or additionally, a sum of the second time period and thethird time period (i.e., TRANS at active voltage level) is equal to onehalf period value of REF_CLK. For example, the sum of the second andthird time periods is represented by time period between points t3 andt5. As discussed above with reference to the sum of the first and secondtime periods, the time period between points t3 and t5 is one halfperiod of REF_CLK when REF_CLK and DIV_CLK both have a 50% duty cycle.In some embodiments, a sum of the first, second, and third time periodscan be less than a period of REF_CLK. For example, the sum of the first,second, and third time periods is represented by a sum of time periodsfrom points t1 to t2 and points t3 to t5. The period of REF_CLK isrepresented by a time period between points t1 and t5, which is alwaysmore than the sum of time periods from points t1 to t2 and points t3 tot5.

An operation of SHR loop filter 220 is described below. For the timeperiod before point t1, CLR is set to an active voltage level to enabledischarging of sampling capacitor, C1. Between points t1 and t2 (thefirst time period), switch S1 (driven by CHRG) is closed, and switchesS2 (driven by CLR) and S3 (driven by TRANS) are opened. Hence, currentsource Ip charges sampling capacitor C1, and increases voltage level Vx.At point t2, Vx is at a voltage level that is lower than the voltagelevel Vo (from the previous clock cycle). The values of Vx and Vo areheld constant until point t3, when TRANS signal becomes an activevoltage level. Between points t3 and t4 (the third time period), switchS3 is closed, and switches S1 and S2 are opened, and a charge onsampling capacitor C1 and holding capacitor C2 is distributed amongstboth capacitors C1 and C2 until the voltage levels Vx and Vo aresubstantially the same. That is, a charge is transferred betweensampling capacitor C1 and holding capacitor C2 during the third timeperiod until plates of capacitors C1 and C2 connected to switch S3 aresubstantially at the same voltage level. Because Vo is higher than Vx atpoint t3, Vx's voltage level increases and Vo's voltage level decreasesuntil they both remain identical until point t4. Between points t4 andt5 (the second time period), switch S2 is closed, and switches S1 and S3are opened, such that sampling capacitor C1 is discharged and voltagelevel Vx becomes an inactive voltage level (i.e., GND). Voltage level Voremains at the same voltage level as at point t4. Time between points t1and t5 marks the first period of REF_CLK.

Time between points t5 and t9 represent a second period of REF_CLK.During a time period between points t5 and t6, current source Ip chargessampling capacitor C1 in the same manner as the operation during thetime period between points t1 and t2, as described above in detail.Because Vx's voltage level was lower than Vo's voltage level during thefirst period, the feedback loop of the PLL can change the VCO output toincrease a phase difference between the rising edges of REF_CLK andDIV_CLK, and thereby increases a pulse width of CHRG signal, as shown intime between points t5 and t6, where a time period from points t5 to t6is larger than a time period from points t1 to t2. Accordingly, thevoltage level Vx at point t6 is larger than the voltage level Vo atpoint t6. Voltage levels Vx and Vo are held constant until point t7, inthe same manner as the operation during a time period from points t2 tot3, as described above in detail. Between points t7 and t8, the chargeon capacitors C1 and C2 is distributed amongst both capacitors C1 and C2until the voltage levels Vx and Vo are substantially the same, in thesame manner as the operation during time period from points t3 to t4, asdescribed above in detail. That is, a charge is transferred betweensampling capacitor C1 and holding capacitor C2 during the time periodfrom points t7 to t8 until plates of capacitors C1 and C2 connected toswitch S3 are substantially at the same voltage level. Because Vx is nowhigher than Vo at point t7, Vo's voltage level increases and Vx'svoltage level decreases until they both remain identical until point t8.Between points t8 and t9, sampling capacitor C1 is discharged andvoltage level Vx becomes an inactive voltage level. Voltage level Voremains at the same voltage level as at point t4.

Time between points t9 and t12 represents a portion of a third period ofREF_CLK. During a time period between points t9 and t10, current sourceIp charges sampling capacitor C1 in the same manner as the operationduring time period between points t1 and t2, described above in detail.Because Vx's voltage level was higher than Vo's voltage level during thesecond period, the feedback loop of the PLL can modify the VCO output todecrease the phase difference between the rising edges of REF_CLK andDIV_CLK, and thereby decreasing the pulse width of CHRG signal, as shownin time between points t9 and t10, where a time period from points t9 tot10 is smaller than a time period from points t5 to t6. The PLL can keepadjusting the phase difference between REF_CLK and DIV_CLK for eachsubsequent period of REF_CLK until the loop reaches a steady-state,where sampling capacitor C1 charges to a voltage level Vx that issubstantially same as the voltage level Vo from the immediately previousperiod. FIG. 3 depicts the third period of REF_CLK as a period where thePLL has reached a steady-state operation. Accordingly, at point t10, thevoltage level Vx is substantially the same as the voltage level Vo.Because the voltage levels Vx and Vo are substantially the same, thereis no charge distribution between capacitors C1 and C2 when switch S3 isclosed from points t11 to t12.

In summary, SHR loop filter 220 generates a control voltage signal thatdetermines the VCO's oscillation frequency, which further determines thedivider clock frequency (e.g., frequency of divider clock signal 145).SHR loop filter 220 generates the VCO control voltage signal based oninput signals CHRG, TRANS, and CLR that control switches S1 through S3.Signals CHRG, TRANS, and CLR are generated by phase detector 110. CHRGsignal drives switch S1 to charge sampling capacitor C1 during a firsttime period of the reference clock signal. CLR signal drives switch S2to discharge sampling capacitor C1 to a low reference voltage during asecond time period different from the first time period. CHRG and CLRsignals aid in setting voltage level Vx by charging and discharging ofsampling capacitor C1. TRANS signal drives switch S3 to distribute of acharge amongst sampling capacitor C1 and holding capacitor C2 during athird time period until both capacitors C1 and C2 have substantially thesame voltage level across the capacitors. A voltage level across holdingcapacitor C2 is voltage Vo that is input as VCO control voltage (e.g.,control voltage signal 125). While PLLs are designed to phase lock at anintended fundamental frequency, PLLs can also phase lock to asub-harmonic frequency as described in FIG. 4 below.

FIG. 4 is a timing diagram illustrating a sub-harmonic locking of a PLL,according to one embodiment. Sub-harmonic locking occurs when phaselocking occurs between the divider clock signal and the reference clocksignal at a frequency of the divider clock signal that corresponds to asub-harmonic of an intended frequency of the VCO output signal. Forexample, when an intended oscillation frequency that is the fundamentalfrequency of the oscillator output signal is 2 GHz, a divide-by-10frequency divider can divide the 2 GHz VCO signal down to 200 MHz. In anormal mode of operation, the PLL phase locks between a 200 MHzreference clock signal and the 200 MHz divider clock signal. If,however, the VCO oscillates at a sub-harmonic of the intended 2 GHz(i.e., at 1 GHz resulting in a 100 MHz divider clock frequency), the PLLcan phase lock between the 200 MHz reference clock signal and the 100MHz divider clock signal. In FIG. 4, x-axis represents time and y-axisrepresents voltage for various signals. Time axis includes variouspoints in time, points t1 through t7, represented by vertical dottedlines. FIG. 4 shows reference clock signal 105 as REF_CLK and dividerclock signal 145 as DIV_CLK.

As shown in FIG. 4, the frequency of DIV_CLK is roughly half of thefrequency of REF_CLK. That is, a period of DIV_CLK is roughly twice thatof REF_CLK. The first rising edge of REF_CLK, as depicted at point t2,triggers the phase detector to generate CHRG signal with an activevoltage level (e.g., close to VDD). The first rising edge of DIV_CLK, asdepicted at point t6, triggers the phase detector to generate CHRGsignal with an inactive voltage level (e.g., close to GND). The firstfalling edge of REF_CLK, as depicted at point t1, triggers the phasedetector to generate TRANS signal with an active voltage level (e.g.,close to VDD). The first falling edge of DIV_CLK, as depicted at pointt3, triggers the phase detector to generate TRANS signal with aninactive voltage level.

As discussed above with reference to FIGS. 2 and 3, CLR signal isgenerated to represent a second time period when each of the signals,REF_CLK, DIV_CLK, and TRANS is at an inactive voltage level. Because theperiod of DIV_CLK is twice that of REF_CLK, REF_CLK toggles whileDIV_CLK remains at an inactive voltage level and while CHRG signal is atan active voltage level. For example, for a time period between pointst4 and t5, when each of the signals, REF_CLK, DIV_CLK, and TRANS is atan inactive voltage level, phase detector generates CLR signal with anactive voltage level, during a time period where CHRG signal is still atan active voltage level. This causes the problem of sub-harmonic lockingas described below.

As shown in FIG. 4, both CHRG and TRANS signals are at an active voltagelevel which results in current source Ip charging both samplingcapacitor C1 and holding capacitor C2 higher to a same voltage levelduring time period from points t2 to t3. Between points t3 and t4, whenTRANS becomes inactive while CHRG remains at an active voltage level,sampling capacitor C1 keeps charging to increase the voltage level Vxwhile holding capacitor C2 holds its charge to keep voltage level Vosame as at point t3. During time between points t4 and t5, CLR signalbecomes active (i.e., CLR signal is pulled to an active voltage level)because each of the signals, REF_CLK, DIV_CLK, and TRANS are at aninactive voltage level. During the time period between points t4 and t5,CLR signal becomes active while CHRG signal also becomes active. Thatis, while CHRG signal is at an active voltage level keeping switch S1closed to keep charging sampling capacitor C1, CLR signal closes switchS2 to discharge sampling capacitor C1. Accordingly, Vx becomes inactiveat point t4 and remains inactive as long as CLR is at an active level,which is until point t5. Between points t5 and t6, CLR signal becomesinactive while CHRG remains at an active voltage level, and samplingcapacitor C1 is charged to a voltage level that is lower than theexisting voltage level Vo. At point t7, CHRG signal goes low and TRANSsignal goes high, and the charge on sampling capacitor C1 and holdingcapacitor C2 is distributed until Vx and Vo reach substantially the samevoltage level. The process described above between points t1 and t7 isrepeated until voltage level Vo reaches a steady-state value thatcorresponds to a sub-harmonic locking of the PLL.

Because CLR signal becomes active to discharge sampling capacitor C1while sampling capacitor C1 is being charged by placing CHRG signalactive, sampling capacitor C1 cannot be charged for the whole durationfor which CHRG is at an active voltage level. Accordingly, if the VCOgenerates an oscillator output signal such that the divider clock signalis at a sub-harmonic frequency of the reference clock signal, the PLLusing a conventional phase detector would result in a sub-harmoniclocking. An embodiment of phase frequency detector (PFD) addressing theissue of sub-harmonic locking is described below in detail withreference to FIGS. 5A and 5B.

FIGS. 5A and 5B show block diagrams illustrating a PFD of a type-I PLLthat can prevent the problem of sub-harmonic locking, according to oneembodiment. The PFD can place a gating element to generate a CLR signalthat helps in preventing a discharging of sampling capacitor C1 during atime period when sampling capacitor C1 is still being charged. FIG. 5Ashows a first portion of the PFD that can generate CHRG signal, and FIG.5B shows a second portion of the PFD that can generate TRANS and CLRsignals. The first portion of the PFD includes, among other components,two D flip-Flops 505 and 510, two inverters 530 and 535, and an OR gate540.

Flip-flop 505 receives REF_CLK as the clock input and its D-input istied to its supply voltage (i.e., VDD to set a logical high value or anactive level). Flip-flop 510 receives DIV_CLK as the clock input and itsD-input is also tied to its supply voltage. At a rising edge of theREF_CLK, flip-flop 505 outputs (CHRG signal) an active level signal andremains at the active level until flip-flop 505 is reset. At the firstrising edge of DIV_CLK after the rising edge of flip-flop 505, theoutput of flip-flop 515 becomes an active level signal. When the outputsignals of both flip-flops 505 and 515 are set to an active level, theoutput of OR gate 540 is set to an inactive level (i.e., GND), and boththe flip-flops, 505 and 515, are reset to change the CHRG signal valueto an inactive voltage level. Because an output of only one flip-flop isused in the PLL, this PFD is a unipolar PFD.

The second portion of the PFD as illustrated in FIG. 5B includes Dflip-flop 550, two AND gates 575 and 585, and five inverters 555, 560,565, 570, and 580. Flip-flop 550 receives REF_CLK as the clock input andits D-input is tied to its supply voltage. At a falling edge of theREF_CLK, flip-flop 550 outputs an active level signal and remains at theactive level until flip-flop 550 is reset. Flip-flop 550's output Q ispassed through inverters 560 and 565, and the output of inverter 565 isTRANS signal. Accordingly, TRANS signal reaches an active level when(after propagation delay of inverters 560 and 565) flip-flop 550's Qoutput reaches an active level. TRANS signal remains at an active leveluntil flip-flop 550 is reset. When DIV_CLK reaches an inactive value (atthe first falling edge of DIV_CLK after the falling edge of REF_CLK),flip-flop 550 is reset to set its Q output as an inactive level. TRANSsignal will follow the Q output to an inactive level after thepropagation delay of inverters 560 and 565.

Gating element 585 shown in FIG. 5B generates CLR signal that controlsswitch S2 to discharge sampling capacitor C1 to a low reference voltage(e.g., ground of the SHR loop filter). In one embodiment, gating element585 is a digital gate performing a logical AND operation. For example,gating element 585 can be a 2-input AND gate shown in FIG. 5B. 2-inputAND gate 585 receives an inverted version of CHRG signal as the firstinput and the output of AND gate 575 as the second input to generate CLRsignal. AND gate 585's first input is an output of inverter 580 thatreceives CHRG signal as its input. AND gate 575 is a 3-input AND gatethat receives an inverted version of signals, TRANS, DIV_CLK, andREF_CLK. 2-input AND gate 585 and 3-input AND gate 575 can be combinedlogically to effectively result in a 4-input AND gate (not shown). Thefour inputs of the 4-input AND gate are inverted versions of signals,TRANS, REF_CLK, DIV_CLK, and CHRG. That is, CLR signal reaches an activevoltage level (i.e., close to VDD) only when all of the signals, TRANS,REF_CLK, DIV_CLK, and CHRG are at an inactive voltage level (i.e., closeto GND). In other words, the PFD generates CLR signal to control switchS2 to discharge sampling capacitor C1 such that sampling capacitor C1 isdischarged only when sampling capacitor C1 is not being charged, andalso only when there is no charge distribution between samplingcapacitor C1 and holding capacitor C2. This prevents the discharging ofsampling capacitor C1 while it is still being charged during a timeperiod between points t4 and t5 of FIG. 4.

By preventing discharging of sampling capacitor C1 when it is beingcharged, the PLL can avoid the sub-harmonic locking problem. Referringback to FIG. 4, when using the PFD depicted in FIGS. 5A and 5B, samplingcapacitor C1 will not discharge and accordingly Vx will not switch to aninactive level at point t4. Instead, sampling capacitor C1 will keepcharging for as long as CHRG signal remains at an active level (i.e.,until point t6) and voltage level Vx will also keep increasing. Later atpoint t7, when TRANS signal reaches an active level, a chargedistribution occurs between sampling capacitor C1 and holding capacitorC2, and the voltage level Vo increases until Vx and Vo are atsubstantially the same voltage level. After some number of REF_CLKperiods, voltage level Vo increases to a sufficient level to lock thedivider clock signal to a fundamental frequency (instead of asub-harmonic frequency) of the reference clock. In this way, the problemof sub-harmonic locking can be prevented.

Even though FIG. 5B shows feeding the output of inverter 560 as input toAND gate 575 (and not an actual inverted version of signal TRANS), aninverted version of TRANS and the output of inverter 560 are logicallythe same signals.

FIG. 6 is a flowchart depicting an operation of a type-I PLL, accordingto one embodiment. First, an SHR loop filter can generate 610 a filteroutput signal based on at least a charge output signal (e.g., CHRGsignal) controlling the time at which a sampling capacitor of the loopfilter is charged. For example, SHR loop filter generates Vo outputsignal based at least on CHRG signal as described above with referenceto FIGS. 2 and 3. In one embodiment, the filter output signal can begenerated based on other signals such as a transfer output signal (e.g.,TRANS signal) that controls a switch to transfer a charge between thesampling capacitor and a holding capacitor. Alternatively, the filteroutput signal can be generated based on other signals such as a clearoutput signal (e.g., CLR signal) that causes the sampling capacitor todischarge charge stored in the sampling capacitor to a low referencevoltage of the loop filter. A relationship between the TRANS and CLRsignals, and filter output signal Vo is also described above withreference to FIGS. 2 and 3.

A VCO of the PLL can generate 620 an oscillator output signal with afrequency corresponding to the filter output signal. A frequency dividercan generate 630 a divider clock signal by performing a frequencydivision on the oscillator output signal, the divider clock signalhaving a same phase as the oscillator output signal but a frequencydifferent than the oscillator output signal. For example, if thefrequency divider divides by an integer 4 and if the VCO produces anoscillator output signal at 4 GHz, the frequency divider will divide the4 GHz into a divider clock signal at 1 GHz but with the same phase asthat of the 4 GHz oscillator output signal.

A PFD can generate 640 the charge output signal (i.e., CHRG signal) tocontrol a switch to charge the sampling capacitor during a first timeperiod set to prevent locking of the PLL at a frequency corresponding toa sub-harmonic frequency of an intended VCO output signal. For example,the first time period is from points t1 to t2 of FIG. 3. The first timeperiod can be defined by a pulse width of CHRG signal such that thepulse width of the charge output signal increases as a phase differencebetween the reference clock signal and the divider clock signalincreases, and the pulse width of the charge output signal decreases asthe phase difference decreases. The PFD can also generate a clear outputsignal (e.g., CLR signal) that causes the sampling capacitor todischarge a charge of the sampling capacitor to a low reference voltageof the loop filter during a second time period, the second time periodis a time period different from the first time period. For example, thesecond time period is from points t4 to t5 of FIG. 3.

The PFD can further generate a transfer output signal (e.g., TRANSsignal) that causes a transfer a charge between the sampling capacitorand the holding capacitor during a third time period, the third timeperiod is a time period different from the second time period. Forexample, the third time period is from points t3 to t4 of FIG. 3. Thethird time period can be defined by a pulse width of the transfer outputsignal such that the pulse width of the transfer output signal increasesas the phase difference between the reference clock signal and thedivider clock signal increases, and the pulse width of the transfersignal decreases as the phase difference decreases.

To prevent locking of the PLL at a frequency of the divider clock signalthat corresponds to a sub-harmonic of a frequency of the oscillatoroutput signal, the CLR signal is generated to be at an active levelduring the second time period during which a charge is not transferredbetween the sampling capacitor and the holding capacitor, and alsoduring which each of the divider clock signal and the reference clocksignal is at an inactive voltage level.

In one embodiment, a sum of the first time period and the second timeperiod is equal to one half period value of the reference clock signal(i.e., REF_CLK). Alternatively or additionally, a sum of the second timeperiod and the third time period is equal to one half period value ofREF_CLK. Alternatively or additionally, a sum of the first, second, andthird time periods can be less than a period of REF_CLK. A relationshipbetween the first, second, and third time periods are described abovewith reference to FIG. 2.

FIG. 7 is a block diagram of a special-purpose computing device that canstore a representation of a PLL, according to one embodiment. In oneembodiment, a representation of a type-I PLL or components within thePLL can be stored as data at in a non-transitory computer-readablemedium (e.g., non-volatile memory 718). The representation can be at abehavioral level, register transfer level, logic component level,transistor level, and layout geometry-level of the PLL.

In some embodiments, computer 700 comprises an interconnect or bus 702(or other communication means) for transmission of data. Computer 700can include a processing means such as one or more processors 704coupled with bus 702 for processing information. Processors 704 cancomprise one or more physical processors and/or one or more logicalprocessors. While bus 702 is illustrated as a single interconnect forsimplicity, it is understood that bus 702 can represent multipledifferent interconnects or buses. Bus 702 shown in FIG. 7 is anabstraction that represents any one or more separate physical buses,point to point connections, or both connected by appropriate bridges,adapters, controllers and/or the like.

In some embodiments, computer 700 further comprises a random accessmemory (RAM) or other dynamic storage device depicted as main memory 712for storing information and instructions to be executed by processors704. Main memory 712 can include an active storage of applicationsincluding a browser application for using in network browsing activitiesby a user of computer 700. Main memory 712 can further include certainregisters or other special purpose memory.

Computer 700 can also comprise a read only memory (ROM) 716 or otherstatic storage device for storing static information and instructionsfor processors 704. Computer 700 can further include one or morenon-volatile memory elements 718 for the storage of certain elements,including, for example, flash memory, a hard disk, solid-state drive.Non-volatile memory elements 718 can store a representation of a type-IPLL described above with references to FIGS. 2 through 5, or componentswithin the PLL, can be stored as data. The representation can be at abehavioral level, register transfer level, logic component level,transistor level, and layout geometry-level of the PLL.

Computer 700 can comprise transceiver module 720 that is coupled to bus702. Transceiver module 720 can further comprise a transmitter moduleand a receiver module. Transceiver module 720 comprises one or moreports 722 to connect to other devices (not shown).

Computer 700 can also comprise circuit logic 740 coupled to bus 702 andconfigured to detect information from a second device (not shown)coupled through ports 722. Computer 700 can also comprise output display726 and coupled via bus 702. In some embodiments, display 726 caninclude a liquid crystal display (LCD) or any other display technology,for displaying information or content to a user, includingthree-dimensional (3D) displays. Alternatively, display 726 can includea touch screen that can also be part of input device 724. In someenvironments, display 726 can include an audio device, such as a speakerfor providing audio information. Computer 700 can also comprise powerdevice 730 that can comprise a power supply, a battery, a solar cell, afuel cell, or other device for providing or generating power. Any powerprovided by power device 730 can be distributed as required to elementsof computer 700.

While particular embodiments and applications of the present disclosurehave been illustrated and described, it is to be understood that theembodiments are not limited to the precise construction and componentsdisclosed herein and that various modifications, changes and variationsmay be made in the arrangement, operation and details of the method andapparatus of the present disclosure disclosed herein without departingfrom the spirit and scope of the disclosure as defined in the appendedclaims.

What is claimed is:
 1. A phase-locked loop (PLL) comprising: a loopfilter comprising a sampling capacitor and a holding capacitor coupledin parallel via a switching element, the loop filter configured togenerate a filter output signal based at least on a charge output signalindicating a first time period during which the sampling capacitor ischarged; a voltage controlled oscillator (VCO) coupled to the loopfilter and configured to generate an oscillator output signal with afrequency corresponding to the filter output signal; a divider coupledto the VCO to receive the oscillator output signal, the dividerconfigured to perform frequency division on the oscillator output signalto generate a divider clock signal having a same phase as the oscillatoroutput signal but a frequency different than the oscillator outputsignal; and a phase frequency detector coupled to the divider to receivethe divider clock signal, the phase frequency detector configured togenerate the charge output signal based on a phase difference betweenthe divider clock signal and a reference clock signal, the phasefrequency detector further configured to prevent locking of the PLL at asub-harmonic of a frequency of the oscillator output signal, the phasefrequency detector comprising a gating element configured to generate aclear output signal causing the sampling capacitor to discharge chargestored in the sampling capacitor to a low reference voltage of the loopfilter during a second time period defined as a period during which acharge is not transferred between the sampling capacitor and the holdingcapacitor via the switching element, and during which the divider clocksignal and the reference clock signal are inactive.
 2. The PLL of claim1, wherein the gating element is a digital gate performing a logical ANDoperation.
 3. The PLL of claim 1, wherein a sum of the first time periodand the second time period is equal to one half period of the referenceclock signal.
 4. The PLL of claim 1, wherein the phase frequencydetector is further configured to generate a transfer output signalcausing a transfer of charge between the sampling capacitor and theholding capacitor during a third time period different from the secondtime period.
 5. The PLL of claim 4, wherein the third time period isdefined by a pulse width of the transfer output signal, the pulse widthof the transfer output signal increases as the phase differenceincreases and the pulse width of the transfer signal decreases as thephase difference decreases.
 6. The PLL of claim 4, wherein a sum of thefirst time period, the second time period, and the third time period isless than a period of the reference clock signal.
 7. The PLL of claim 4,wherein a sum of the second time period and the third time period isequal to one half period of the reference clock signal.
 8. The PLL ofclaim 1, wherein the first time period is defined by a pulse width ofthe charge output signal, the pulse width of the charge output signalincreases as the phase difference increases and the pulse width of thecharge signal decreases as the phase difference decreases.
 9. A methodfor operating a phase-locked loop (PLL), comprising: generating, by aloop filter, a filter output signal based at least on a charge outputsignal; generating, by a voltage controlled oscillator, an oscillatoroutput signal with a frequency corresponding to the filter outputsignal; generating, by a divider, a divider clock signal by performing afrequency division on the oscillator output signal, the divider clocksignal having a same phase as the oscillator output signal but afrequency different than the oscillator output signal; generating, by aphase frequency detector, the charge output signal to charge a samplingcapacitor during a first time period set to prevent locking of the PLLat a frequency that is a sub-harmonic of a frequency of the oscillatoroutput signal; and generating, by the phase frequency detector, a clearoutput signal causing the sampling capacitor to discharge a chargestored in the sampling capacitor to a low reference voltage of the loopfilter during a second time period defined as a period during which acharge is not transferred between the sampling capacitor and the holdingcapacitor, and during which each of the divider clock signal and thereference clock signal is inactive.
 10. The method of claim 9, wherein asum of the first time period and the second time period is equal to onehalf period of the reference clock signal.
 11. The method of claim 9,further comprising: generating, by the phase frequency detector, atransfer output signal to transfer a charge between the samplingcapacitor and the holding capacitor during a third time period differentfrom the second time period.
 12. The method of claim 11, wherein thethird time period is defined by a pulse width of the transfer outputsignal, the pulse width of the transfer output signal increasing as aphase difference between the reference clock signal and the dividerclock signal increases, and the pulse width of the transfer signaldecreasing as the phase difference decreases.
 13. The method of claim11, wherein a sum of the first time period, the second time period, andthe third time period is less than a period of the reference clocksignal.
 14. The method of claim 11, wherein a sum of the second timeperiod and the third time period is equal to one half period of thereference clock signal.
 15. The method of claim 9, wherein the firsttime period is defined by a pulse width of the charge output signal, thepulse width of the charge output signal increases as the phasedifference between the reference clock signal and the divider clocksignal increases, and the pulse width of the charge output signaldecreases as the phase difference decreases.
 16. A non-transitorycomputer-readable medium storing a representation of a phase-locked loop(PLL), the PLL comprising: a loop filter comprising a sampling capacitorand a holding capacitor coupled in parallel via a switching element, theloop filter configured to generate a filter output signal based at leaston a charge output signal indicating a first time period during whichthe sampling capacitor is charged; a voltage controlled oscillator (VCO)coupled to the loop filter and configured to generate an oscillatoroutput signal with a frequency corresponding to the filter outputsignal; a divider coupled to the VCO to receive the oscillator outputsignal, the divider configured to perform frequency division on theoscillator output signal to generate a divider clock signal having asame phase as the oscillator output signal but a frequency differentthan the oscillator output signal; and a phase frequency detectorcoupled to the divider to receive the divider clock signal, the phasefrequency detector configured to generate the charge output signal basedon a phase difference between the divider clock signal and a referenceclock signal, the phase frequency detector further configured to preventlocking of the PLL at a sub-harmonic of a frequency of the oscillatoroutput signal, the phase frequency detector comprising a gating elementconfigured to generate a clear output signal causing the samplingcapacitor to discharge charge stored in the sampling capacitor to a lowreference voltage of the loop filter during a second time period definedas a period during which a charge is not transferred between thesampling capacitor and the holding capacitor via the switching element,and during which the divider clock signal and the reference clock signalare inactive.